# Telegrapher's equations

The telegrapher's equations (or just telegraph equations) are a pair of coupled, linear differential equations that describe the voltage and current on an electrical transmission line with distance and time. The equations come from Oliver Heaviside who in the 1880s developed the transmission line model. The model demonstrates that the electromagnetic waves can be reflected on the wire, and that wave patterns can appear along the line. The theory applies to transmission lines of all frequencies including high-frequency transmission lines (such as telegraph wires and radio frequency conductors), audio frequency (such as telephone lines), low frequency (such as power lines) and direct current.

## Distributed components

The telegrapher's equations, like all other equations describing electrical phenomena, result from Maxwell's equations. In a more practical approach, one assumes that the conductors are composed of an infinite series of two-port elementary components, each representing an infinitesimally short segment of the transmission line:

• The distributed resistance $R$ of the conductors is represented by a series resistor (expressed in ohms per unit length).
• The distributed inductance $L$ (due to the magnetic field around the wires, self-inductance, etc.) is represented by a series inductor (henries per unit length).
• The capacitance $C$ between the two conductors is represented by a shunt capacitor C (farads per unit length).
• The conductance $G$ of the dielectric material separating the two conductors is represented by a shunt resistor between the signal wire and the return wire (siemens per unit length). This resistor in the model has a resistance of $1/G$ ohms.

The model consists of an infinite series of the infinitesimal elements shown in the figure, and that the values of the components are specified per unit length so the picture of the component can be misleading. An alternative notation is to use $R'$ , $L'$ , $C'$ , and $G'$ to emphasize that the values are derivatives with respect to length. These quantities can also be known as the primary line constants to distinguish from the secondary line constants derived from them, these being the characteristic impedance, the propagation constant, attenuation constant and phase constant. All these constants are constant with respect to time, voltage and current. They may be non-constant functions of frequency.

### Role of different components Schematic showing a wave flowing rightward down a lossless transmission line. Black dots represent electrons, and the arrows show the electric field.

The role of the different components can be visualized based on the animation at right.

• The inductance L makes it look like the current has inertia—i.e. with a large inductance, it is difficult to increase or decrease the current flow at any given point. Large inductance makes the wave move more slowly, just as waves travel more slowly down a heavy rope than a light one. Large inductance also increases the wave impedance (lower current for the same voltage).
• The capacitance C controls how much the bunched-up electrons within each conductor repel the electrons in the other conductor. By absorbing some of these bunched up electrons, the speed of the wave and its strength (voltage) are both reduced. With a larger capacitance, there is less repulsion, because the other line (which always has the opposite charge) partly cancels out these repulsive forces within each conductor. Larger capacitance equals (weaker restoring force)s making the wave move slightly slower, and also gives the transmission line a lower impedance (higher current for the same voltage).
• R corresponds to resistance within each line, and G allows current to flow from one line to the other. The figure at right shows a lossless transmission line, where both R and G are 0.

### Values of primary parameters for telephone cable

Representative parameter data for 24 gauge telephone polyethylene insulated cable (PIC) at 70 °F (294 K)

Frequency R L G C
Hz Ωkm Ω1000 ft mHkm mH1000 ft µSkm µS1000 ft nFkm nF1000 ft
1 Hz 172.24 52.50 0.6129 0.1868 0.000 0.000 51.57 15.72
1 kHz 172.28 52.51 0.6125 0.1867 0.072 0.022 51.57 15.72
10 kHz 172.70 52.64 0.6099 0.1859 0.531 0.162 51.57 15.72
100 kHz 191.63 58.41 0.5807 0.1770 3.327 1.197 51.57 15.72
1 MHz 463.59 141.30 0.5062 0.1543 29.111 8.873 51.57 15.72
2 MHz 643.14 196.03 0.4862 0.1482 53.205 16.217 51.57 15.72
5 MHz 999.41 304.62 0.4675 0.1425 118.074 35.989 51.57 15.72

More extensive tables and tables for other gauges, temperatures and types are available in Reeve. Chen gives the same data in a parameterized form that he states is usable up to 50 MHz.

The variation of $R$ and $L$ is mainly due to skin effect and proximity effect.

The constancy of the capacitance is a consequence of intentional, careful design.

The variation of G can be inferred from Terman: “The power factor ... tends to be independent of frequency, since the fraction of energy lost during each cycle ... is substantially independent of the number of cycles per second over wide frequency ranges.” A function of the form $G(f)=G_{1}\left({\frac {f}{f_{1}}}\right)^{g_{\mathrm {e} }}$ with $g_{\mathrm {e} }$ close to 1.0 would fit Terman’s statement. Chen  gives an equation of similar form.

G in this table can be modeled well with

$f_{1}=1\;\mathrm {MHz}$ $G_{1}=29.11\;\mathrm {\mu S/km} =8.873\;\mathrm {\mu S/{1000ft}}$ $g_{\mathrm {e} }=0.87$ Usually the resistive losses grow proportionately to $f^{0.5}\,$ and dielectric losses grow proportionately to $f^{g_{\mathrm {e} }}\,$ with $g_{\mathrm {e} }>0.5$ so at a high enough frequency, dielectric losses will exceed resistive losses. In practice, before that point is reached, a transmission line with a better dielectric is used. In long distance rigid coaxial cable, to get very low dielectric losses, the solid dielectric may be replaced by air with plastic spacers at intervals to keep the center conductor on axis.

### The equations

The telegrapher's equations are:

{\begin{aligned}{\frac {\ \partial }{\partial x}}\ V(x,t)&=-L\ {\frac {\ \partial }{\partial t}}\ I(x,t)-R\ I(x,t)\\{\frac {\ \partial }{\partial x}}\ I(x,t)&=-C\ {\frac {\ \partial }{\partial t}}V(x,t)-G\ V(x,t)\\\end{aligned}} They can be combined to get two partial differential equations, each with only one dependent variable, either $V$ or $I\,$ :

{\begin{aligned}{\frac {~\ \partial ^{2}}{\partial x^{2}}}\ V(x,t)&-LC\ {\frac {~\ \partial ^{2}}{\ \partial t^{2}}}\ V(x,t)&=(RC+GL)\ {\frac {\ \partial }{\partial t}}\ V(x,t)&+GR\ V(x,t)\\{\frac {~\ \partial ^{2}}{\partial x^{2}}}\ I(x,t)&-LC\ {\frac {~\ \partial ^{2}}{\partial t^{2}}}\ I(x,t)&=(RC+GL)\ {\frac {\ \partial }{\partial t}}\ I(x,t)&+GR\ I(x,t)\\\end{aligned}} Except for the dependent variable ($\,V$ or $I\,$ ) the formulas are identical.

## Lossless transmission

When the elements R and G are very small, their effects can be neglected, and the transmission line is considered as an ideal lossless structure. In this case, the model depends only on the L and C elements. The Telegrapher's Equations then describe the relationship between the voltage V and the current I along the transmission line, each of which is a function of position x and time t:

$V=V(x,t)$ $I=I(x,t)$ ### The equations for lossless transmission lines

The equations themselves consist of a pair of coupled, first-order, partial differential equations. The first equation shows that the induced voltage is related to the time rate-of-change of the current through the cable inductance, while the second shows, similarly, that the current drawn by the cable capacitance is related to the time rate-of-change of the voltage.

${\frac {\partial V}{\partial x}}=-L{\frac {\partial I}{\partial t}}$ ${\frac {\partial I}{\partial x}}=-C{\frac {\partial V}{\partial t}}$ The Telegrapher's Equations are developed in similar forms in the following references: Kraus, Hayt, Marshall, Sadiku, Harrington, Karakash, and Metzger.

These equations may be combined to form two exact wave equations, one for voltage V, the other for current I:

${\frac {\partial ^{2}V}{{\partial t}^{2}}}-u^{2}{\frac {\partial ^{2}V}{{\partial x}^{2}}}=0$ ${\frac {\partial ^{2}I}{{\partial t}^{2}}}-u^{2}{\frac {\partial ^{2}I}{{\partial x}^{2}}}=0$ where

$u={\frac {1}{\sqrt {LC}}}$ is the propagation speed of waves traveling through the transmission line. For transmission lines made of parallel perfect conductors with vacuum between them, this speed is equal to the speed of light.

In the case of sinusoidal steady-state, the voltage and current take the form of single-tone sine waves:

$V(x,t)=\mathrm {Re} \{V(x)\cdot e^{j\omega t}\}$ $I(x,t)=\mathrm {Re} \{I(x)\cdot e^{j\omega t}\}$ ,

where $\omega$ is the angular frequency of the steady-state wave. In this case, the Telegrapher's equations reduce to

${\frac {dV}{dx}}=-j\omega LI$ ${\frac {dI}{dx}}=-j\omega CV$ Likewise, the wave equations reduce to

${\frac {d^{2}V}{dx^{2}}}+k^{2}V=0$ ${\frac {d^{2}I}{dx^{2}}}+k^{2}I=0$ where k is the wave number:

$k=\omega {\sqrt {LC}}={\omega \over u}.$ Each of these two equations is in the form of the one-dimensional Helmholtz equation.

In the lossless case, it is possible to show that

$V(x)=V_{1}e^{-jkx}+V_{2}e^{+jkx}$ and

$I(x)={V_{1} \over Z_{0}}e^{-jkx}-{V_{2} \over Z_{0}}e^{+jkx}$ where $k$ is a real quantity that may depend on frequency and $Z_{0}$ is the characteristic impedance of the transmission line, which, for a lossless line is given by

$Z_{0}={\sqrt {L \over C}}$ and $V_{1}$ and $V_{2}$ are arbitrary constants of integration, which are determined by the two boundary conditions (one for each end of the transmission line).

This impedance does not change along the length of the line since L and C are constant at any point on the line, provided that the cross-sectional geometry of the line remains constant.

The lossless line and distortionless line are discussed in Sadiku, and Marshall,

### General solution

The general solution of the wave equation for the voltage is the sum of a forward traveling wave and a backward traveling wave:

$V(x,t)\ =\ f_{1}(x-ut)+f_{2}(x+ut)$ where

• $f_{1}$ and $f_{2}$ can be any functions whatsoever, and
• $u={\frac {1}{\sqrt {LC}}}$ is the waveform's propagation speed (also known as phase velocity).

f1 represents a wave traveling from left to right in a positive x direction whilst f2 represents a wave traveling from right to left. It can be seen that the instantaneous voltage at any point x on the line is the sum of the voltages due to both waves.

Since the current I is related to the voltage V by the telegrapher's equations, we can write

$I(x,t)\ =\ {\frac {f_{1}(x-ut)}{Z_{0}}}-{\frac {f_{2}(x+ut)}{Z_{0}}}$ ## Lossy transmission line

When the loss elements R and G are not negligible, the differential equations describing the elementary segment of line are

{\begin{aligned}{\frac {\partial }{\partial x}}V(x,t)&=-L{\frac {\partial }{\partial t}}I(x,t)-RI(x,t)\\{\frac {\partial }{\partial x}}I(x,t)&=-C{\frac {\partial }{\partial t}}V(x,t)-GV(x,t)\\\end{aligned}} By differentiating both equations with respect to x, and some algebraic manipulation, we obtain a pair of hyperbolic partial differential equations each involving only one unknown:

{\begin{aligned}{\frac {\partial ^{2}}{{\partial x}^{2}}}V&=LC{\frac {\partial ^{2}}{{\partial t}^{2}}}V+(RC+GL){\frac {\partial }{\partial t}}V+GRV\\{\frac {\partial ^{2}}{{\partial x}^{2}}}I&=LC{\frac {\partial ^{2}}{{\partial t}^{2}}}I+(RC+GL){\frac {\partial }{\partial t}}I+GRI\\\end{aligned}} Note that these equations resemble the homogeneous wave equation with extra terms in V and I and their first derivatives. These extra terms cause the signal to decay and spread out with time and distance. If the transmission line is only slightly lossy (R << ωL and G << ωC), signal strength will decay over distance as e−αx, where α ≈ R/2Z0 + GZ0/2.:130

## Signal pattern examples Changes of the signal level distribution along the single dimensional transmission medium. Depending on the parameters of the telegraph equation, this equation can reproduce all four patterns.

Depending on the parameters of the telegraph equation, the changes of the signal level distribution along the length of the single-dimensional transmission medium may take the shape of the simple wave, wave with decrement, or the diffusion-like pattern of the telegraph equation. The shape of the diffusion-like pattern is caused by the effect of the shunt capacitance.

## Solutions of the telegrapher's equations as circuit components Equivalent circuit of an unbalanced transmission line (such as coaxial cable) where: 2/Z = trans-admittance of VCCS (Voltage Controlled Current Source), X = length of transmission line, Z(s) = characteristic impedance, T(s) = propagation function, γ(s) = propagation "constant", s = jω, j²=-1. Note: Rω, Lω, Gω and Cω may be functions of frequency. Equivalent circuit of a balanced transmission line (such as twin-lead) where: 2/Z = trans-admittance of VCCS (Voltage Controlled Current Source), X = length of transmission line, Z(s) = characteristic impedance, T(s) = propagation function, γ(s) = propagation "constant", s = jω, j²=-1. Note: Rω, Lω, Gω and Cω may be functions of frequency.

The solutions of the telegrapher's equations can be inserted directly into a circuit as components. The circuit in the top figure implements the solutions of the telegrapher's equations.

The bottom circuit is derived from the top circuit by source transformations. It also implements the solutions of the telegrapher's equations.

The solution of the telegrapher's equations can be expressed as an ABCD type two-port network with the following defining equations

{\begin{aligned}V_{1}&=V_{2}\cosh(\gamma x)+I_{2}Z\sinh(\gamma x)\\I_{1}&=V_{2}{\frac {1}{Z}}\sinh(\gamma x)+I_{2}\cosh(\gamma x).\\\end{aligned}} The ABCD type two-port gives $V_{1}\,$ and $I_{1}\,$ as functions of $V_{2}\,$ and $I_{2}\,$ . Both of the circuits above, when solved for $V_{1}\,$ and $I_{1}\,$ as functions of $V_{2}\,$ and $I_{2}\,$ yield exactly the same equations.

In the bottom circuit, all voltages except the port voltages are with respect to ground and the differential amplifiers have unshown connections to ground. An example of a transmission line modeled by this circuit would be a balanced transmission line such as a telephone line. The impedances Z(s), the voltage dependent current sources (VDCSs) and the difference amplifiers (the triangle with the number "1") account for the interaction of the transmission line with the external circuit. The T(s) blocks account for delay, attenuation, dispersion and whatever happens to the signal in transit. One of the T(s) blocks carries the forward wave and the other carries the backward wave. The circuit, as depicted, is fully symmetric, although it is not drawn that way. The circuit depicted is equivalent to a transmission line connected from $V_{1}\,$ to $V_{2}\,$ in the sense that $V_{1}\,$ , $V_{2}\,$ , $I_{1}\,$ and $I_{2}$ would be same whether this circuit or an actual transmission line was connected between $V_{1}\,$ and $V_{2}\,$ . There is no implication that there are actually amplifiers inside the transmission line.

Every two-wire or balanced transmission line has an implicit (or in some cases explicit) third wire which may be called shield, sheath, common, Earth or ground. So every two-wire balanced transmission line has two modes which are nominally called the differential and common modes. The circuit shown on the bottom only models the differential mode.

In the top circuit, the voltage doublers, the difference amplifiers and impedances Z(s) account for the interaction of the transmission line with the external circuit. This circuit, as depicted, is also fully symmetric, and also not drawn that way. This circuit is a useful equivalent for an unbalanced transmission line like a coaxial cable or a microstrip line.

These are not the only possible equivalent circuits.